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LTC4365 Datasheet

Linear Technology/Analog Devices

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Datasheet

LTC4365
1
4365fa
For more information www.linear.com/LTC4365
Typical applicaTion
FeaTures DescripTion
Overvoltage,
Undervoltage and Reverse
Supply Protection Controller
12V Automotive Application
applicaTions
n Wide Operating Voltage Range: 2.5V to 34V
n Overvoltage Protection to 60V
n Reverse Supply Protection to –40V
n LTC4365: Blocks 50Hz and 60Hz AC Power
n LTC4365-1: Fast (1ms) Recovery from Fault
n No Input Capacitor or TVS Required for Most
Applications
n Adjustable Undervoltage and Overvoltage
Protection Range
n Charge Pump Enhances External N-Channel MOSFET
n Low Operating Current: 125µA
n Low Shutdown Current: 10µA
n Compact 8-Lead, 3mm × 2mm DFN and
TSOT-23 (ThinSOT™) Packages
n Portable Instrumentation
n Industrial Automation
n Laptops
n Automotive Surge Protection
L, LT , LT C , LT M , Linear Technology and the Linear logo are registered trademarks and
ThinSOT and Hot Swap are trademarks of Linear Technology Corporation. All other trademarks
are the property of their respective owners.
Load Protected from Reverse and Overvoltage at VIN
The LT C
®
4365 protects applications where power supply
input voltages may be too high, too low or even negative.
It does this by controlling the gate voltages of a pair of
external N-channel MOSFETs to ensure that the output
stays within a safe operating range.The LTC4365 can
withstand voltages between –40V and 60V and has an
operating range of 2.5V to 34V, while consuming only
125µA in normal operation.
Tw o comparator inputs allow configuration of the over-
voltage (OV) and undervoltage (UV) set points using an
external resistive divider. A shutdown pin provides external
control for enabling and disabling the MOSFETs as well
as placing the device in a low current shutdown state. A
fault output provides status of the gate pin pulling low. A
fault is indicated when the part is in shutdown or the input
voltage is outside the UV and OV set points.
The LTC4365 has a 36ms turn-on delay that debounces
live connections and blocks 50Hz to 60Hz AC power. For
fast recovery after faults, the LTC4365-1 has a reduced
1ms turn-on delay.
–30V
GND
10V/DIV
30V
4365 TA01b
1s/DIV
UV = 3.5V
OV = 18V
VOUT
VOUT
VIN
VIN
VALID
WINDOW
VIN
UV
OV
SHDN
OV = 18V
UV = 3.5V
4365 TA01a
VOUT
FAULT
GATE
VIN
12V
VOUT
3A
Si4946
GND
LTC4365
510k
1820k
243k
59k
LTC4365
2
4365fa
For more information www.linear.com/LTC4365
pin conFiguraTion
absoluTe MaxiMuM raTings
Supply Voltage (Note 1)
VIN .......................................................... 40V to 60V
Input Voltages (Note 3)
UV, SHDN .............................................. 0.3V to 60V
OV ............................................................ 0.3V to 6V
VOUT....................................................... 0.3V to 40V
Output Voltages (Note 4)
FA U LT ..................................................... 0.3V to 60V
GATE ....................................................... –40V to 45V
TOP VIEW
9
GND
DDB PACKAGE
8-LEAD (3mm × 2mm) PLASTIC DFN
5
6
7
8
4
3
2
1GND
OV
UV
VIN
SHDN
FAULT
VOUT
GATE
TJMAX = 150°C, θJA = 76°C/W
EXPOSED PAD (PIN 9) PCB GROUND CONNECTION OPTIONAL
1
2
3
4
8
7
6
5
TOP VIEW
TS8 PACKAGE
8-LEAD PLASTIC TSOT-23
GATE
VOUT
FAULT
SHDN
VIN
UV
OV
GND
TJMAX = 150°C, θJA = 195°C/W
Input Currents
UV, OV, SHDN .................................................... –1mA
Operating Ambient Temperature Range
LTC4365C ................................................ C to 70°C
LTC4365I .............................................40°C to 85°C
LTC4365H .......................................... 40°C to 125°C
Storage Temperature Range .................. 65°C to 150°C
Lead Temperature (Soldering, 10 sec)
for TSOT Only ................................................... 300°C
LTC4365
3
4365fa
For more information www.linear.com/LTC4365
Lead Free Finish
TAPE AND REEL (MINI) TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE
LTC4365CDDB#TRMPBF LTC4365CDDB#TRPBF LFKS 8-Lead (3mm × 2mm) Plastic DFN 0°C to 70°C
LTC4365CDDB-1#TRMPBF LTC4365CDDB-1#TRPBF LGMB 8-Lead (3mm × 2mm) Plastic DFN 0°C to 70°C
LTC4365IDDB#TRMPBF LTC4365IDDB#TRPBF LFKS 8-Lead (3mm × 2mm) Plastic DFN –40°C to 85°C
LTC4365IDDB-1#TRMPBF LTC4365IDDB-1#TRPBF LGMB 8-Lead (3mm × 2mm) Plastic DFN –40°C to 85°C
LTC4365HDDB#TRMPBF LTC4365HDDB#TRPBF LFKS 8-Lead (3mm × 2mm) Plastic DFN –40°C to 125°C
LTC4365HDDB-1#TRMPBF LTC4365HDDB-1#TRPBF LGMB 8-Lead (3mm × 2mm) Plastic DFN –40°C to 125°C
LTC4365CTS8#TRMPBF LTC4365CTS8#TRPBF LTFKT 8-Lead Plastic TSOT-23 0°C to 70°C
LTC4365CTS8-1#TRMPBF LTC4365CTS8-1#TRPBF LTGKZ 8-Lead Plastic TSOT-23 0°C to 70°C
LTC4365ITS8#TRMPBF LTC4365ITS8#TRPBF LTFKT 8-Lead Plastic TSOT-23 –40°C to 85°C
LTC4365ITS8-1#TRMPBF LTC4365ITS8-1#TRPBF LTGKZ 8-Lead Plastic TSOT-23 –40°C to 85°C
LTC4365HTS8#TRMPBF LTC4365HTS8#TRPBF LTFKT 8-Lead Plastic TSOT-23 –40°C to 125°C
LTC4365HTS8-1#TRMPBF LTC4365HTS8-1#TRPBF LTGKZ 8-Lead Plastic TSOT-23 –40°C to 125°C
TRM = 500 pieces. *Temperature grades are identified by a label on the shipping container.
Consult LT C Marketing for parts specified with wider operating temperature ranges.
Consult LT C Marketing for information on lead based finish parts.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
elecTrical characTerisTics
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
VIN, VOUT
VIN Input Voltage Range Operating Range
Protection Range
l
l
2.5
–40
34
60
V
V
IVIN Input Supply Current SHDN = 0V, VIN = VOUT, –40°C to 85°C
SHDN = 0V, VIN = VOUT, –40°C to 125°C
SHDN = 2.5V
l
l
l
10
10
25
50
100
150
µA
µA
µA
IVIN(R) Reverse Input Supply Current VIN = –40V, VOUT = 0V l–1.2 –1.8 mA
VIN(UVLO) Input Supply Undervoltage Lockout VIN Rising l1.8 2.2 2.4 V
IVOUT VOUT Input Current SHDN = 0V, VIN = VOUT
SHDN = 2.5V, VIN = VOUT
VIN = –40V, VOUT = 0V
l
l
l
6
100
20
30
250
50
µA
µA
µA
GATE
ΔVGATE N-Channel Gate Drive
(GATE-VOUT)
VIN = VOUT = 5.0V, IGATE = –1µA
VIN = VOUT = 12V to 34V, IGATE = –1µA
l
l
3
7.4
3.6
8.4
4.2
9.8
V
V
IGATE(UP) N-Channel Gate Pull Up Current GATE = VIN = VOUT = 12V l–12 –20 –30 µA
IGATE(FAST) N-Channel Gate Fast Pull Down Current Fast Shutdown, GATE = 20V, VIN = VOUT = 12Vl31 50 72 mA
IGATE(SLOW)N-Channel Gate Gentle Pull Down Current Gentle Shutdown, GATE = 20V, VIN = VOUT = 12Vl50 90 150 µA
tGATE(FAST) N-Channel Gate Fast Turn Off Delay CGATE = 2.2nF, UV or OV Fault l2 4 µs
tGATE(SLOW)N-Channel Gentle Turn Off Delay CGATE = 2.2nF, SHDN Falling, VIN = VOUT = 12Vl150 250 350 µs
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 2.5V to 34V, unless otherwise noted. (Note 2)
orDer inForMaTion
LTC4365
4
4365fa
For more information www.linear.com/LTC4365
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
tRECOVERY GATE Recovery Delay Time VIN = 12V, Power Good to ΔVGATE > 0V
LTC4365, CGATE = 2.2nF
LTC4365-1, CGATE = 2.2nF
l
l
26
0.6
36
1
49
1.5
ms
ms
UV, OV
VUV UV Input Threshold Voltage UV Falling ΔVGATE = 0V l492.5 500 507.5 mV
VOV OV Input Threshold Voltage OV Rising ΔVGATE = 0V l492.5 500 507.5 mV
VUVHYST UV Input Hysteresis l20 25 32 mV
VOVHYST OV Input Hysteresis l20 25 32 mV
ILEAK UV, OV Leakage Current V = 0.5V, VIN = 34V l±10 nA
tFAULT UV, OV Fault Propagation Delay Overdrive = 50mV
VIN = VOUT = 12V
l1 2 µs
SHDN
VSHDN SHDN Input Threshold SHDN Falling to ΔVGATE = 0V l0.4 0.75 1.2 V
ISHDN SHDN Input Current SHDN = 0.75V, VIN = 34V l±10 nA
tSTART Delay Coming Out of Shutdown Mode SHDN Rising to ΔVGATE > 0V, VIN = VOUT = 12Vl400 800 1200 µs
tSHDN(F) SHDN to FAULT Asserted VIN = VOUT = 12V l1.5 3 µs
tLOWPWR Delay from Turn Off to Low Power Operation VIN = VOUT = 12V
LTC4365
LTC4365-1
l
l
26
0.3
36
0.7
55
2
ms
ms
FAUL
T
VOL FAULT Output Voltage Low IFAULT = 500µA l0.15 0.4 V
IFAULT FAULT Leakage Current FAULT = 5V, VIN = 34V l±20 nA
Note 1. Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2. All currents into pins are positive; all voltages are referenced to
GND unless otherwise noted.
Note 3. These pins can be tied to voltages below –0.3V through a resistor
that limits the current below 1mA.
Note 4. The GATE pin is referenced to VOUT and does not exceed 44V for
the entire operating range.
elecTrical characTerisTics
The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 2.5V to 34V, unless otherwise noted. (Note 2)
LTC4365
5
4365fa
For more information www.linear.com/LTC4365
Typical perForMance characTerisTics
VOUT Operating Current vs
Temperature
VOUT Shutdown Current vs
Temperature VOUT Current vs Reverse VIN
VIN Operating Current vs
Temperature VIN Shutdown Current vs VIN VIN Current vs VIN (–40 to 60V)
GATE Current vs GATE Drive
GATE Drive vs VIN GATE Drive vs Temperature
TEMPERATURE (°C)
–50
0
I
VIN
(µA)
20
40
60
80
0 50 100
4365 G01
100
–25 25 75 125
SHDN = 2.5V
VIN = 12V
VIN = 34V
VOUT = VIN
VIN = 2.5V
VIN (V)
0
0
I
VIN
(µA)
5
10
15
25
20
10 20 3530
4365 G02
30
5 15 25
VIN = VOUT
SHDN = 0V
25°C
45°C
125°C
70°C
VIN (V)
–50
–1600
IVIN (µA)
–1200
–800
–400
0
0 50 75
4365 G03
400
–25 25
SHDN = UV = 0V
25°C
25°C
–45°C
125°C
TEMPERATURE (°C)
–50
0
IVOUT (µA)
40
80
120
160
0 10075 125
200
–25 25 50
SHDN = 2.5V
VOUT = 34V
VOUT = 12V
VOUT = 2.5V
VIN = VOUT
TEMPERATURE (°C)
–50
0
IVOUT (µA)
5
10
15
0 25 75 100 125
4365 G05
20
–25 50
SHDN = 0V
VOUT = 34V
VOUT = 12V
VOUT = 2.5V
VIN = VOUT
VIN (V)
0
I
VOUT
(µA)
5
10
15
20
0 –10 –30 –40 –50
4365 G06
25
–20
45°C
25°C
125°C
VOUT = 0V
VIN (V)
0
∆V
GATE
(V)
2
4
6
8
10
0 5 15 20 3525 30
4365 G07
12
10
VOUT = 0V
VOUT = VIN
T = 25°C
IGATE = –1µA
TEMPERATURE (°C)
–50
0
∆V
GATE
(V)
2
4
6
8
0 50 100
4365 G08
10
–25 25 75 125
VIN = VOUT = 12V
VIN = VOUT = 34V
IGATE = –1µA
VIN = VOUT = 2.5V
∆VGATE (V)
0
0
IGATE(UP) (µA)
–5
–10
–15
–20
2 6 10
4365 G09
–25
48
VIN = VOUT = 12V
125°C
25°C
–45°C
LTC4365
6
4365fa
For more information www.linear.com/LTC4365
UV/OV Propagation Delay vs
Overdrive
Recovery Delay Time vs
Temperature
LTC4365 Recovery Delay Time
vs VIN
OV Threshold vs Temperature UV/OV Leakage vs Temperature
UV Threshold vs Temperature
Typical perForMance characTerisTics
TEMPERATURE (°C)
–50
492.5
V
UV
(mV)
495.0
497.5
500.0
502.5
505.0
0 50 100
4365 G10
507.5
–25 25 75 125
VIN = VOUT = 12V
TEMPERATURE (°C)
–50
492.5
VOV (mV)
495.0
497.5
500.0
502.5
505.0
0 50 100
4365 G11
507.5
–25 25 75 125
VIN = VOUT = 12V
TEMPERATURE (°C)
–75
0
I
LEAK
(nA)
0.25
0.50
0.75
4365 G12
1.00
–25 25 75 175125
VUV/OV = 0.5V
VIN = 12V
UV
OV
OVERDRIVE (mV)
1
0
t
FAULT
(µs)
8
4
12
16
4365 G13
20
10 100 1000
VIN = VOUT = 12V
T = 25°C
TEMPERATURE (°C)
–50
0
t
RECOVERY
(ms)
10
20
30
40
50
0 50 100
4365 G14
–25 25 75 125
VIN = 34V
VIN = 12V
VIN = 2.5V
VIN (V)
0
0
tRECOVERY (ms)
10
20
30
40
50
10 20 35
4365 G15
5 15 3025
125°C
25°C
–45°C
4365 G16
2.5ms/DIV
GATE
VOUT
VIN
10µF, 1k LOAD ON VOUT
60V DUAL NCH MOSFET
1V/DIV
20V/DIV GND
GND
4365 G17
250µs/DIV
VOUT
GATE
100µF, 12Ω LOAD ON VOUT
60V SI9945 DUAL NCH MOSFET
VIN = 12V
SHDN
5V/DIV
3V/DIV GND
GND
4365 G18
250µs/DIV
VOUT
SHDN
GATE 100µF, 12Ω LOAD ON VOUT
60V SI9945 DUAL NCH MOSFET
5V/DIV
3V/DIV
GND
GND
LTC4365 AC Blocking Turn-On Timing Turn-Off Timing
LTC4365
7
4365fa
For more information www.linear.com/LTC4365
pin FuncTions
Exposed Pad: Connect to device ground.
FAULT: Fault Indication Output. This high voltage open drain
output is pulled low if UV is below its monitor threshold,
if OV is above its monitor threshold, if SHDN is low, or if
VIN has not risen above VIN(UVLO).
GATE: Gate Drive Output for External N-channel MOSFETs.
An internal charge pump provides 20µA of pull-up current
and up to 9.8V of enhancement to the gate of an external
N-channel MOSFET.
When turned off, GATE is pulled just below the lower of
VIN or VOUT. When VIN goes negative, GATE is automati-
cally connected to VIN.
GND: Device Ground.
OV: Overvoltage Comparator Input. Connect this pin to an
external resistive divider to set the desired VIN overvoltage
fault threshold. Input to an accurate, fast (1µs) compara-
tor with a 0.5V rising threshold and 25mV of hysteresis.
When OV rises above its threshold, a 50mA current sink
pulls down on the GATE output. When OV falls back below
0.475V, and after a 36ms recovery delay waiting period
(1ms for LTC4365-1), the GATE charge pump is enabled.
The low leakage current of the OV input allows the use
of large valued resistors for the external resistive divider.
Connect to GND if unused.
SHDN: Shutdown Control Input. SHDN high enables the
GATE charge pump which in turn enhances the gate of an
external N-channel MOSFET. A low on SHDN generates a
pull down on the GATE output with a 90µA current sink and
places the LTC4365 in low current mode (10µA). If unused,
connect to VIN. If VIN goes below ground, or if VIN rings
to 60V, use a current limiting resistor of at least 100k.
UV: Undervoltage Comparator Input. Connect this pin to an
external resistive divider to set the desired VIN undervoltage
fault threshold. Input to an accurate, fast (1µs) compara-
tor with a 0.5V falling threshold and 25mV of hysteresis.
When UV falls below its threshold, a 50mA current sink
pulls down on the GATE output. When UV rises back above
0.525V, and after a 36ms recovery delay waiting period
(1ms for LTC4365-1), the GATE charge pump is enabled.
The low leakage current of the UV input allows the use
of large valued resistors for the external resistive divider.
If unused, connect to VIN. While connected to VIN, if VIN
goes below ground, or if VIN rings to 60V, use a current
limiting resistor of at least 100k.
VIN: Power Supply Input. Maximum protection range:
–40V to 60V. Operating range: 2.5V to 34V.
VOUT: Output Voltage Sense Input. This pin senses the volt-
age at the output side of the external N-channel MOSFET.
The GATE charge pump voltage is referenced to VOUT. It
is used as the charge pump input when VOUT is greater
than approximately 6.5V.
LTC4365
8
4365fa
For more information www.linear.com/LTC4365
block DiagraM
VIN
–40V TO 60V
5V INTERNAL
SUPPLY
6.5V INTERNAL
SUPPLY
LDO
2.2V
UVLO
0.5V
GND
25mV
HYSTERESIS
4365 BD
IGATE
REVERSE
PROTECTION
CLOSES SWITCH
WHEN VIN IS NEGATIVE
ENABLE
GATE PULLDOWN
FAULT
OFF
TURN
OFF
50mA 9A
SHDN SHDN
GATE
CHARGE
PUMP
f = 400kHz
VOUT
UV
OV
+
DELAY TIMERS
LOGIC
+
+
FAULT
GATE
Many of today’s electronic systems get their power from
external sources such as wall wart adapters, batteries and
custom power supplies. A typical supply arrangement for
a portable product is shown by the operational diagram
in Figure 1. Power is supplied by an AC adaptor or, if the
plug is withdrawn, by a removable battery. Trouble arises
when any of the following occurs:
• The battery is installed backwards
• An AC adaptor of opposite polarity is attached
• An AC adaptor of excessive voltage is attached
• The battery is discharged below a safe level
This can lead to supply voltages that are too high, too
low, or even negative. If these power sources are applied
directly to the electronic systems, the systems could be
subject to damage. The LTC4365 is an input voltage fault
protection N-channel MOSFET controller. The part isolates
an input supply from its load to protect the load from
unexpected supply voltage conditions, while providing a
low loss path for qualified power.
To protect electronic systems from improperly connected
power supplies, system designers will often add discrete
diodes, transistors and high voltage comparators. The high
voltage comparators enable system power only if the input
supply falls within a desired voltage window. A Schottky
diode or P-channel MOSFET typically added in series with
the supply protects against reverse supply connections.
The LTC4365 provides accurate overvoltage and under-
voltage comparators to ensure that power is applied to
operaTion
LTC4365
9
4365fa
For more information www.linear.com/LTC4365
operaTion
the system only if the input supply meets the user select-
able voltage window. Reverse supply protection circuits
automatically isolate the load from negative input voltages.
During normal operation, a high voltage charge pump
applicaTions inForMaTion
The LTC4365 is an N-channel MOSFET controller that
protects a load from faulty supply connections. A basic
application circuit using the LTC4365 is shown in Figure 2
The circuit provides a low loss connection from VIN to
VOUT as long as the voltage at VIN is between 3.5V and
VIN
UV
OV
SHDN
OV = 18V
UV = 3.5V
4365 F02
VOUT
FAULT
GATE
VIN
12V NOMINAL
VOUT
3.5V TO 18V
Si4946
60V DUAL
GND
LTC4365
R5
100k
COUT
100µF
R3
1820k
R2
243k
R1
59k
+
M1 M2
Figure 1. Operational Diagram Common to Many Portable Products
18V. Voltages at VIN outside of the 3.5V to 18V range are
prevented from getting to the load and can be as high as
60V and as low as –40V. The circuit of Figure 2 protects
against negative voltages at VIN as shown. No other external
components are needed.
During normal operation, the LTC4365 provides up to
9.8V of gate enhancement to the external back-to-back
N-channel MOSFETs. This turns on the MOSFET, thus
connecting the load at VOUT to the supply at VIN.
GATE Drive
The LTC4365 turns on the external N-channel MOSFETs by
driving the GATE pin above VOUT. The voltage difference
between the GATE and VOUT pins (gate drive) is a function
of VIN and VOUT.
enhances the gate of external N-channel power MOSFETs.
Power consumption is 10µA during shutdown and 125µA
while operating. The LTC4365 integrates all these func-
tions in tiny TSOT-23 and 3mm × 2mm DFN packages.
VIN
UV
OV
SHDN
2.5V TO 34V
OPERATING RANGE
4365 F01
VOUT
FAULT
GATE
GND
LTC4365
R5
R3
BATTERY
–40V TO 60V PROTECTION RANGE
AC
ADAPTOR
INPUT
OV, UV PROTECTION
THRESHOLDS SET TO
SATISFY LOAD CIRCUIT
R2
R1
M1 M2
LOAD
CIRCUIT
+
Figure 2. LTC4365 Protects Load from –40V
to 60V VIN Faults
LTC4365
10
4365fa
For more information www.linear.com/LTC4365
Overvoltage and Undervoltage Protection
The LTC4365 provides two accurate comparators to moni-
tor for overvoltage (OV) and undervoltage (UV) conditions
at VIN. If the input supply rises above the user adjustable
OV threshold, the gate of the external MOSFET is quickly
turned off, thus disconnecting the load from the input.
Similarly, if the input supply falls below the user adjust-
able UV threshold, the gate of the external MOSFET also
is quickly turned off. Figure 4 shows a UV/OV application
for an input supply of 12V.
Figure 3. Gate Drive (GATE – VOUT) vs VOUT
applicaTions inForMaTion
Figure 3 highlights the dependence of the gate drive on VIN
and VOUT. When system power is first turned on (SHDN
low to high, VOUT = 0V), gate drive is at a maximum for all
values of VIN. This helps prevent start-up problems into
heavy loads by ensuring that there is enough gate drive
to support the load.
As VOUT ramps up from 0V, the absolute value of the GATE
voltage remains fixed until VOUT is greater than the lower
of (VIN –1V) or 6V. Once VOUT crosses this threshold,
gate drive begins to increase up to a maximum of 9.8V
(for VIN ≥ 12V). The curves of Figure 3 were taken with
a GATE load of –1µA. If there were no load on GATE, the
gate drive for each VIN would be slightly higher.
Note that when VIN is at the lower end of the operating
range, the external N-channel MOSFET must be selected
with a corresponding lower threshold voltage.
VIN
12V
UVTH = 3.5V
OVTH = 18V
4365 F04
DISCHARGE GATE
WITH 50mA SINK
LTC4365
OV
COMPARATOR
UV
COMPARATOR
R3
1820k
UV
0.5V
0.5V
OV
R2
243k
R1
59k
+
25mV
+
25mV
Figure 4. UV, OV Comparators Monitor 12V Supply
The external resistive divider allows the user to select
an input supply range that is compatible with the load at
VOUT. Furthermore, the UV and OV inputs have very low
leakage currents (typically < 1nA at 100°C), allowing for
large values in the external resistive divider. In the applica-
tion of Figure 4, the load is connected to the supply only if
VIN lies between 3.5V and 18V. In the event that VIN goes
above 18V or below 3.5V, the gate of the external N-channel
MOSFET is immediately discharged with a 50mA current
sink, thus isolating the load from the supply.
Table 1 lists some external MOSFETs compatible with
different VIN supply voltages.
Table 1. Dual MOSFETs for Various Supply Ranges
VIN MOSFET VTH(MAX) VGS(MAX) VDS(MAX)
2.5V SiB914 0.8V 5V 8V
3.3V Si5920 1.0V 5V 8V
5V Si7940 1.5V 8V 12V
≤30V Si4214 3.0V 20V 30V
≤60V Si9945 3.0V 20V 60V
VOUT (V)
0
0
∆VGATE (V)
2
4
6
10
8
12
915
4365 F03
3 6 12
VIN = 30V
VIN = 12V
VIN = 5V
VIN = 3.3V
VIN = 2.5V
T = 25°C
IGATE = –1µA
LTC4365
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For more information www.linear.com/LTC4365
Figure 5 shows the timing associated with the UV pin.
Once a UV fault propagates through the UV comparator
(tFAULT), the FAULT output is asserted low and a 50mA
current sink discharges the GATE pin. As VOUT falls, the
GATE pin tracks VOUT.
applicaTions inForMaTion
Figure 6 shows the timing associated with the OV pin.
Once an OV fault propagates through the OV comparator
(tFAULT), the FAULT output is asserted low and a 50mA
current sink discharges the GATE pin. As VOUT falls, the
GATE pin tracks VOUT.
Procedure for Selecting UV/OV External Resistor Values
The following 3-step procedure helps select the resistor
values for the resistive divider of Figure 4. This procedure
minimizes UV and OV offset errors caused by leakage
currents at the respective pins.
1. Choose maximum tolerable offset at the UV pin,
VOS(UV). Divide by the worst case leakage current at
the UV pin, IUV (10nA). Set the sum of R1 + R2 equal
to VOS(UV) divided by 10nA. Note that due to the
presence of R3, the actual offset at UV will be slightly
lower:
R1+R2 =
V
OS(UV)
IUV
2. Select the desired VIN UV trip threshold, UVTH. Find
the value of R3:
R3 =
V
OS(UV)
IUV
UV
TH
– 0.5V
0.5V
3. Select the desired VIN OV trip threshold, OVTH. Find
the values of R1 and R2:
R1=
VOS(UV)
IUV
+R3
OVTH
0.5V
R2 =
V
OS(UV)
IUV
– R1
The example of Figure 4 uses standard 1% resistor values.
The following parameters were selected:
VOS(UV) = 3mV
IUV = 10nA
UVTH = 3.5V
OVTH = 18V
4365 F05
FAULT
GATE
tFAULT
tGATE(FAST)
VUV VUV + VUVHYST
tFAULT
tRECOVERY
EXTERNAL N-CHANNEL MOSFET
TURNS OFF
UV
4365 F06
FAULT
GATE
tFAULT
tGATE(FAST)
VOV VOV – VOVHYST
tFAULT
tRECOVERY
EXTERNAL N-CHANNEL MOSFET
TURNS OFF
OV
Figure 5. UV Timing (OV < (VOV – VOVHYST), SHDN > 1.2V)
Figure 6. OV Timing (UV > (VUV + VUVHYST), SHDN > 1.2V)
When both the UV and OV faults are removed, the external
MOSFET is not immediately turned on. The input supply
must remain within the user selected power good window
for at least 36ms (tRECOVERY) before the load is again
connected to the supply. This recovery timeout period
filters noise (including line noise) at the input supply and
prevents chattering of power at the load. For applications
that require faster turn-on after a fault, the LTC4365-1
provides a 1ms recovery timeout period.
LTC4365
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For more information www.linear.com/LTC4365
applicaTions inForMaTion
The resistor values can then be solved:
1. R1+R2 =
3mV
10nA
=300k
2. R3 =2
3mV
10nA
(3.5V – 0.5V) =1.8M
The closest 1% value: R3 = 1.82M:
3. R1 =
300k +1.82M
218V
=58.9k
The closest 1% value: R1 = 59k:
R2 = 300k – 59k = 241k
The closest 1% value: R2 = 243k
Therefore: OV = 17.93V, UV = 3.51V.
Reverse VIN Protection
The LTC4365’s rugged and hot-swappable VIN input helps
protect the more sensitive circuits at the output load. If
the input supply is plugged in backwards, or a negative
supply is inadvertently connected, the LTC4365 prevents
this negative voltage from passing to the output load.
The LTC4365 employs a novel, high speed reverse supply
voltage monitor. When the negative VIN voltage is detected,
an internal switch connects the gates of the external back-
to-back N-channel MOSFETs to the negative input supply.
As shown in Figure 7, external back-to-back N-channel
MOSFETs are required for reverse supply protection. When
VIN goes negative, the reverse VIN comparator closes the
internal switch, which in turn connects the gates of the
external MOSFETs to the negative VIN voltage. The body
diode (D1) of M1 turns on, but the body diode (D2) of
M2 remains in reverse blocking mode. This means that
the common source connection of M1 and M2 remains
about a diode drop higher than VIN. Since the gate voltage
of M2 is shorted to VIN, M2 will be turned off and no cur-
rent can flow from VIN to the load at VOUT. Note that the
voltage rating of M2 must withstand the reverse voltage
excursion at VIN.
Figure 8 illustrates the waveforms that result when VIN
is hot plugged to –20V. VIN, GATE and VOUT start out at
ground just before the connection is made. Due to the
parasitic inductance of the VIN and GATE connections, the
voltage at the VIN and GATE pins ring significantly below
–20V. Therefore, a 40V N-channel MOSFET was selected
to survive the overshoot.
The speed of the LTC4365 reverse protection circuits is
evident by how closely the GATE pin follows VIN during
the negative transients. The two waveforms are almost
indistinguishable on the scale shown.
The trace at VOUT, on the other hand, does not respond
to the negative voltage at VIN, demonstrating the desired
reverse supply protection. The waveforms of Figure 8 were
captured using a 40V dual N-channel MOSFET, a 10µF
ceramic output capacitor and no load current on VOUT.
Figure 7. Reverse VIN Protection Circuits
VIN
4365 F07
VOUT
GATE
VIN = –40V
REVERSE VIN
COMPARATOR
CLOSES SWITCH
WHEN VIN IS NEGATIVE
GND
LTC4365
M1
D1 D2
M2
+
+
TO LOAD
COUT
Figure 8. Hot Swapping VIN to –20V
–20V
5V/DIV
GND
4365 F07
500ns/DIV
GATE
VOUT
VIN
LTC4365
13
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For more information www.linear.com/LTC4365
Recovery Timer
The LTC4365 has a recovery delay timer that filters noise
at VIN and helps prevent chatter at VOUT. After either an
OV or UV fault has occurred, the input supply must return
to the desired operating voltage window for at least 36ms
(tRECOVERY) in order to turn the external MOSFET back on
as illustrated in Figure 5 and Figure 6. For applications
that require faster turn-on after a fault, the LTC4365-1
provides a 1ms recovery timeout period.
Going out of and then back into fault in less than tRECOVERY
will keep the MOSFET off continuously. Similarly, coming
out of shutdown (SHDN low to high) triggers an 800µs
start-up delay timer (see Figure 11).
The recovery timer is also active while the part is power-
ing up. The recovery timer starts once VIN rises above
VIN(UVLO) and VIN lies within the user selectable UV/OV
power good window. See Figure 9.
Gentle Shutdown
The SHDN input turns off the external MOSFETs in a gentle,
controlled manner. When SHDN is asserted low, a 90µA
current sink slowly begins to turn off the external MOSFETs.
Once the voltage at the GATE pin falls below the voltage
at the VOUT pin, the current sink is throttled back and a
feedback loop takes over. This loop forces the GATE voltage
to track VOUT, thus keeping the external MOSFETs off as
VOUT decays. Note that when VOUT < 4.5V, the GATE pin
is pulled to within 400mV of ground.
Gentle gate turn off reduces load current slew rates and
mitigates voltage spikes due to parasitic inductances. To
further decrease GATE pin slew rate, place a capacitor
across the gate and source terminals of the external MOS-
FETs. The waveforms of Figure 10 were captured using
the Si4214 dual N-channel MOSFETs, and a 2A load with
100µF output capacitor.
applicaTions inForMaTion
4365 F09
GATE MOSFET OFF MOSFET ON
VIN VIN(UVLO)
tRECOVERY
Figure 9. Recovery Timing During Power-On (OV
= GND, UV = SHDN = VIN)
Figure 10. Gentle Shutdown: GATE Tracks VOUT as VOUT Decays
GATE
VOUT
tGATE(SLOW)
GATE = VOUT
tSTART
tSHDN(F)
VGATE
SHDN
4365 F11
FAULT
Figure 11. Gentle Shutdown Timing
FAULT Status
The FAULT high voltage open drain output is driven low if
SHDN is asserted low, if VIN is outside the desired UV/OV
voltage window, or if VIN has not risen above VIN(UVLO).
Figure 5, Figure 6 and Figure 11 show the FAULT output
timing.
5V/DIV
4365 F10
100µs/DIV
GATE
VOUT
SHDN
VIN = 12V
T = 25°C
GND
Select Between Tw o Input Supplies
With the part in shutdown, the VIN and VOUT pins can be
driven by separate power supplies. The LTC4365 then
automatically drives the GATE pin just below the lower of
LTC4365
14
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For more information www.linear.com/LTC4365
the two supplies, thus turning off the external back-to-back
MOSFETs. The application of Figure 12 uses two LTC4365s
to select between two power supplies. Care should be taken
to ensure that only one of the two LTC4365s is enabled
at any given time.
applicaTions inForMaTion
Figure 12. Selecting One of Tw o Supplies
VIN
V2
SHDN
4365 F12
VOUT
GATE
LTC4365
VIN
V1
SEL
0
1
OUT
V1
V2
OUT
M2M1
M2M1
SEL
SHDN
VOUT
GATE
LTC4365
Limiting Inrush Current During Turn-On
The LTC4365 turns on the external N-channel MOSFET
with a 20µA current source. The maximum slew rate at
the GATE pin can be reduced by adding a capacitor on
the GATE pin:
Slew Rate =
20µA
C
GATE
Since the MOSFET acts like a source follower, the slew
rate at VOUT equals the slew rate at GATE.
Therefore, inrush current is given by:
IINRUSH =
C
OUT
C
GATE
20µA
For example, a 1A inrush current to a 330µF output
capacitance requires a GATE capacitance of:
CGATE =
20µA C
OUT
I
INRUSH
CGATE =
20µA 330µF
1A
=6.6nF
The 6.8nF CGATE capacitor in the application circuit of
Figure 14 limits the inrush current to approximately 1A.
RGATE makes sure that CGATE does not affect the fast GATE
turn off characteristics during UV/OV faults, or during
reverse VIN connection. R4A and R4B help prevent high
frequency oscillations with the external N-channel MOSFET
and related board parasitics.
VIN
UV
OV
SHDN
OV = 30V
4365 F13
VOUT
FAULT
GATE
VIN
24V
SI7120DN
60V VOUT
GND
LTC4365
R2
2370k
R1
40.2k
COUT
100µF
+
R5
100k
Figure 13. Small Footprint Single MOSFET Application
Protects Against 60V
4365 F14
VIN
VIN VOUT
R4B
10Ω
R4A
10Ω
COUT
330µF
VOUT
GATE
LTC4365
RGATE
5.1k
CGATE
6.8nF
+
M2M1
Figure 14. Limiting Inrush Current with CGATE
Single MOSFET Application
When reverse VIN protection is not needed, only a single
external N-channel MOSFET is necessary. The applica-
tion circuit of Figure 13 connects the load to VIN when
VIN is less than 30V, and uses the minimal set of external
components.
LTC4365
15
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For more information www.linear.com/LTC4365
applicaTions inForMaTion
Transients During OV Fault
The circuit of Figure 15 was used to display transients
during an overvoltage condition. The nominal input supply
is 24V and it has an overvoltage threshold of 30V. The
parasitic inductance is that of a 1 foot wire (roughly 300nH).
Figure 16 shows the waveforms during an overvoltage
condition at VIN. These transients depend on the parasitic
inductance and resistance of the wire along with the ca-
pacitance at the VIN node. D1 is an optional power clamp
(TVS, Tranzorb) recommended for applications where
the DC input voltage can exceed 24V and with large VIN
parasitic inductance. No clamp was used to capture the
waveforms of Figure 16. In order to maintain reverse sup-
ply protection, D1 must be a bi-directional clamp rated for
at least 225W peak pulse power dissipation.
VIN
UV
OV
SHDN
OV = 30V
4365 F15
VOUT
FAULT
GATE
M1 M2
VIN
24V
SI9945
60V
12 INCH WIRE
LENGTH VOUT
GND
LTC4365
R2
2370k
R1
40.2k
R3
100k
COUT
100µF
+
CIN
1000µF
D1
OPTIONAL
+
2A/DIV
GND
GND
0A
20V/DIV
20V/DIV
4365 F16
250ns/DIV
GATE
VOUT
VIN
IIN
GATE
VOUT
Figure 15. OV Fault with Large VIN Inductance
Figure 16. Transients During OV Fault When No
Tranzorb (TVS) Is Used
LTC4365
16
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For more information www.linear.com/LTC4365
REGULATOR APPLICATIONS
Hysteretic Regulator
Built-in hysteresis and the availability of both inverting
and noninverting control inputs (OV and UV) facilitate the
design of hysteretic regulators. Figure 17 shows how the
LTC4365-1 can protect a load from OV transients, while
regulating the output voltage at a user-defined level. When
the output voltage reaches its OV limit, the LTC4365-1
turns off the external MOSFETs. The load current then
discharges the output capacitance until OV falls below the
hysteresis voltage. The external MOSFETs are turned back
on after a 1ms delay. Figure 18 shows the waveforms for
the circuit of Figure 17. Note that the duration, magnitude
and duty cycle of the VIN glitch must not exceed the SOA
rating of the external MOSFETs.
Solar Charger
Figure 19 shows a series regulator for a solar charger.
The LTC4365-1 connects the solar charger to the battery
when the battery voltage falls below 13.9V (after a 1ms
delay). Conversely, when the battery reaches 14.6V, the
LTC4365-1 immediately (2µs) opens the charging path.
Regulation of the battery voltage is achieved by connect-
ing a resistive divider from the battery to the accurate OV
comparator input (with 5% hysteresis). The fast rising
response of the OV comparator prevents the battery voltage
from rising above the user-selected threshold.
applicaTions inForMaTion
Figure 17. Hysteretic Regulation of VOUT During OV Transients Figure 18. VOUT Regulates at 16V When VIN
Glitches Above Desired Level
VIN
UV
OV
SHDN
4365 F17
VOUT
FAULT
GATE
VIN
12V
Si4946
DUAL NCH
OPTIONAL
SNUBBER
VOUT
GND
LTC4365-1
R5
510k
CLOAD
47µF
COV
220pF
+RLOAD
100Ω
R2
1820k
R1
59k
1µF
R7
4365 F18
2.5ms/DIV
5V/DIV
GND
VOUT
VIN
VIN
4365 F19
VOUT GATEUVSHDN
1/2 OF Si4214 1/2 OF Si4214
GND
LTC4365-1
OV
M1
D1
D4
B130
D2
M2
+TO LOAD
CBATT
100µF
CBYP
100nF
15W
SOLAR
PANEL
R2
3.24M
R1
115k
14.6V OFF
13.9V ON
COV
220pF
12V, 8Ah
GELCELL
Figure 19. Series Hysteretic Solar Charger with Reverse-Battery and Solar Panel Protection
LTC4365
17
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For more information www.linear.com/LTC4365
applicaTions inForMaTion
Note that during initial start-up, the LTC4365-1 will not
turn on the external MOSFETs until a battery is first con-
nected to the VIN pin. To begin operation, VIN must initially
rise above the 2.2V UVLO lockout voltage. Connecting the
battery ensures that the LTC4365-1 comes out of UVLO.
12V Application with 150V Transient Protection
Figure 20 shows a 12V application that withstands input
supply transients up to 150V. When the input voltage ex-
ceeds 17.9V, the OV resistive divider turns off the external
MOSFETs. As VIN rises to 150V, the gate of transistor M1
remains in the Off condition, thus preventing conduction
from VIN to VOUT. Note that M1 must have an operating
range above 150V.
Resistor R6 and diode D3 clamp the LTC4365 supply volt-
age to 50V. To prevent R6 from interfering with reverse
operation, the recommended value is 1k or less. Note that
the power handling capability of R6 must be considered in
order to avoid overheating during transients. D3 is shown
as a bidirectional clamp in order to achieve reverse-polarity
protection at VIN. M2 is also required in order to protect
VOUT from negative voltages at VIN and should have an
operating range beyond the breakdown of D3. If reverse
protection is not desired remove M2 and connect the
source of M1 directly to VOUT.
MOSFET Selection
To protect against a negative voltage at VIN, the external
N-channel MOSFETs must be configured in a back-to-
back arrangement. Dual N-channel packages are thus the
best choice. The MOSFET is selected based on its power
handling capability, drain and gate breakdown voltages,
and threshold voltage.
The drain to source breakdown voltage must be higher
than the maximum voltage expected between VIN and VOUT.
Note that if an application generates high energy transients
during normal operation or during Hot Swap™, the external
MOSFET must be able to withstand this transient voltage.
Due to the high impedance nature of the charge pump that
drives the GATE pin, the total leakage on the GATE pin must
be kept low. The gate drive curves of Figure 2 were measured
with aA load on the GATE pin. Therefore, the leakage on
the GATE pin must be no greater thanA in order to match
the curves of Figure 2. Higher leakage currents will result
in lower gate drive. The dual N-channel MOSFETs shown
in Table 1 all have a maximum GATE leakage current of
100nA. Additionally, Table 1 lists representative MOSFETs
that would work at different values of VIN.
Layout Considerations
The trace length between the VIN pin and the drain of the
external MOSFET should be minimized, as well as the trace
length between the GATE pin of the LTC4365 and the gates
of the external MOSFETs.
Place the bypass capacitors at VOUT as close as possible
to the external MOSFET. Use high frequency ceramic
capacitors in addition to bulk capacitors to mitigate Hot
Swap ringing. Place the high frequency capacitors closest
to the MOSFET. Note that bulk capacitors mitigate ringing
by virtue of their ESR. Ceramic capacitors have low ESR
and can thus ring near their resonant frequency.
Figure 20. 12V Application Protected from 150V Transients
VIN
UV
OV
SHDN
OV = 17.9V
D3: SMAJ43CA BI-DIRECTIONAL
4365 F20
VOUT
FAULT
GATE
M1 M2
VIN
12V
FDB33N25
VOUT
GND
LTC4365
R3
510k
D3
R2
2050k
R1
59k
R6
1k
LTC4365
18
4365fa
For more information www.linear.com/LTC4365
package DescripTion
DDB Package
8-Lead Plastic DFN (3mm × 2mm)
(Reference LTC DWG # 05-08-1702 Rev B)
1.50 – 1.75
(NOTE 4)
2.80 BSC
0.22 – 0.36
8 PLCS (NOTE 3)
DATUM ‘A
0.09 – 0.20
(NOTE 3)
TS8 TSOT-23 0710 REV A
2.90 BSC
(NOTE 4)
0.65 BSC
1.95 BSC
0.80 – 0.90
1.00 MAX 0.01 – 0.10
0.20 BSC
0.30 – 0.50 REF
PIN ONE ID
NOTE:
1. DIMENSIONS ARE IN MILLIMETERS
2. DRAWING NOT TO SCALE
3. DIMENSIONS ARE INCLUSIVE OF PLATING
4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
5. MOLD FLASH SHALL NOT EXCEED 0.254mm
6. JEDEC PACKAGE REFERENCE IS MO-193
3.85 MAX
0.40
MAX
0.65
REF
RECOMMENDED SOLDER PAD LAYOUT
PER IPC CALCULATOR
1.4 MIN
2.62 REF
1.22 REF
TS8 Package
8-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1637 Rev A)
2.00 ±0.10
(2 SIDES)
NOTE:
1. DRAWING CONFORMS TO VERSION (WECD-1) IN JEDEC PACKAGE OUTLINE M0-229
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE
0.40 ± 0.10
BOTTOM VIEW—EXPOSED PAD
0.56 ± 0.05
(2 SIDES)
0.75 ±0.05
R = 0.115
TYP
R = 0.05
TYP
2.15 ±0.05
(2 SIDES)
3.00 ±0.10
(2 SIDES)
14
85
PIN 1 BAR
TOP MARK
(SEE NOTE 6)
0.200 REF
0 – 0.05
(DDB8) DFN 0905 REV B
0.25 ± 0.05
2.20 ±0.05
(2 SIDES)
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
0.61 ±0.05
(2 SIDES)
1.15 ±0.05
0.70 ±0.05
2.55
±0.05
PACKAGE
OUTLINE
0.25 ± 0.05
0.50 BSC
PIN 1
R = 0.20 OR
0.25 × 45°
CHAMFER
0.50 BSC
Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.
LTC4365
19
4365fa
For more information www.linear.com/LTC4365
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-
tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
revision hisTory
REV DATE DESCRIPTION PAGE NUMBER
A 09/13 Added LTC4365-1 Information Multiple
Operation section: Rewritten with new Figure 1 8, 9
Table 1: MOSFET for ≤30V changed to Si4214 from Si4230 10
Figure 13: Inserted R5, 100k resistor to SHDN pin 14
Added "Regulator Applications" with three subsections and Figures 17 to 20 16, 17
Updated Typical Application 20
LTC4365
20
4365fa
For more information www.linear.com/LTC4365
LINEAR TECHNOLOGY CORPORATION 2013
LT 0913 REV A • PRINTED IN USA
Linear Technology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 FAX: (408) 434-0507 www.linear.com/LTC4365
relaTeD parTs
Typical applicaTion
LTC4365 Protects Step Down Regulator from –30V to 30V VIN Faults
PART NUMBER DESCRIPTION COMMENTS
LT4363 Surge Stopper Overvoltage/Overcurrent Protection
Regulator
Wide Operating Range: 4V to 80V, Reverse Protection to –60V, Adjustable
Output Clamp Voltage
LTC4364 Surge Stopper with Ideal Diode 4V to 80V Operation, –40V Reverse Input, –20V Reverse Output
LTC4366 Floating Surge Stopper 9V to >500V Operation, 8-Pin TSOT and 3mm × 2mm DFN Packages
LTC4361 Overvoltage/Overcurrent Protection Controllers 5.8V Overvoltage Threshold, 85V Absolute Maximum
LTC2909 Triple/Dual Inputs UV/OV Negative Monitor Pin Selectable Input Polarity Allows Negative and OV Monitoring
LTC2912/LTC2913 Single/Dual UV/OV Voltage Monitor Ads UV and OV Trip Values, ±1.5% Threshold Accuracy
LTC2914 Quad UV/OV Monitor For Positive and Negative Supplies
LTC2955 Pushbutton On/Off Controller Automatic Turn-On, 1.5V to 36V Input, ±36V PB Input
LT4256 Positive 48V Hot Swap Controller with
Open-Circuit Detect
Foldback Current Limiting, Open-Circuit and Overcurrent Fault Output,
Up to 80V Supply
LTC4260 Positive High Voltage Hot Swap Controller with
ADC and I2C
Wide Operating Range 8.5V to 80V
LTC4352 Ideal MOSFET ORing Diode External N-Channel MOSFETs Replace ORing Diodes, 0V to 18V
LTC4354 Negative Voltage Diode-OR Controller Controls Tw o N-Channel MOSFETs, 1.2µs Turn-Off, –80V Operation
LTC4355 Positive Voltage Diode-OR Controller Controls Tw o N-Channel MOSFETs, 0.4µs Turn-Off, 80V Operation
LT1913 Step-Down Switching Regulator 3.6V to 25V Input, 3.5A Maximum Current, 200kHz to 2.4MHz
VIN
UV
OV
SHDN
OV = 18V
UV = 3.5V 4365 TA02
VOUT
FAULT
GATE
Si4214 30V
DUAL N-CHANNEL
VOUT PROTECTED
FROM –30V TO 30V
VIN
12V NOMINAL
VOUT
GND
LTC4365
510k
10µF
1820k
243k
59k
SW
FB
VC
PG
RT
VIN BD
OUTPUT
5V
3.5A
0.47µF
47µF
100k
15k
63.4k
4.7µH
536k
GND
LT1913
RUN/SS BOOST
SYNC
680pF

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IC OVERVOLTAGE PROTECT 8-DFN
Available Quantity2745
Unit Price486
IC OVERVOLTAGE PROT TSOT23-8
Available Quantity1268
Unit Price486
IC OVERVOLTAGE PROT TSOT23-8
Available Quantity9108
Unit Price532
IC OVERVOLTAGE PROT TSOT23-8
Available Quantity1094
Unit Price532
IC OVERVOLTAGE PROTECT 8-DFN
Available Quantity2000
Unit Price441
IC OVERVOLTAGE PROTECT 8-DFN
Available Quantity475
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IC OVERVOLTAGE PROTECT 8-DFN
Available Quantity174
Unit Price532
BOARD EVAL LTC4365CTS8-1
Available Quantity20
Unit Price2878
IC OVERVOLTAGE PROT TSOT23-8
Available Quantity0
Unit Price237.0568
IC OVERVOLTAGE PROT TSOT23-8
Available Quantity0
Unit Price243.734
DEMO BOARD FOR LTC4365
Available Quantity0
Unit Price0